Adaptive antenna receiver

ABSTRACT

A path detector detects multipath waves on a transmission line based on a plurality of despread signals corresponding to fixed directional beams. An adaptive beam forming section forms an adaptive beam combined signal for each path, using a weight generated by an adaptive algorithm and the despread signals. An adder combines the adaptive beam signal for all paths, and a data judging section judges data included in the combined signal.

TECHNICAL FIELD

The present invention relates to an adaptive antenna receiver in amobile communication system that adopts a code division multiple access(hereinafter, “CDMA”) system that uses a spread spectrum modulationsystem. More specifically, the present invention relates to an adaptiveantenna receiver suitable for a transmission line of frequency selectivefading, in which multipath waves interfere with each other due toreflection, diffraction, and scattering of radio waves resulting fromthe surrounding buildings and geographical features.

BACKGROUND ART

A conventional receiver is explained below. Conventional receivers aredescribed, for example, in “Experimental Evaluation on Coherent AdaptiveArray Antenna Diversity for DS-CDMA Reverse Link, The Institute ofElectronics, Information and Communication Engineers, Technical Reportof IEICE, RCS98-94, p. 33-38, September, 1998”, and “LaboratoryExperiments on Coherent Rake Receiver in Broadband DS-CDMA Mobile Radio,The Institute of Electronics, Information and Communication Engineers,Technical Report of IEICE, CS99-129, p. 57-62, October, 1999”.

FIG. 9 shows the configuration of the conventional receiver. In FIG. 9,201-1, 201-2, . . . 201-N denote N antennas, 202-1, 202-2, . . . , 202-Ndenote N band-pass filters (hereinafter, “BPF”), 203-1, 203-2, . . . ,203-N denote N despreading sections, 204 denotes a path detector, 205-1,205-2, . . . , 205-L denote L beam forming sections that receivedespread signals affected by multipath waves, to form beams for eachpath with respect to L paths, 206 denotes an adder, and 207 denotes adata judging section.

In each beam forming section, 221-1, 221-2, . . . , 221-N denote Ncomplex multipliers, 222 denotes a delay device, 223 denotes a weightcontroller, 224 denotes an adder, 225 denotes a complex multiplier, 226denotes a complex conjugate calculator, 227 denotes a complexmultiplier, 228 denotes a subtracter, and 229 denotes a transmissionline estimating section that estimates a transmission line with respectto the individual path.

FIG. 10 shows a detailed configuration of the path detector 204. In thepath detector 204, 300 denotes a transmission line estimating section,301 denotes a mean power value calculator, 302 denotes a thresholdcalculator, 303 denotes a judging section, and 304 denotes a pathselecting section, which detects a plurality of paths from the despreadsignal.

FIG. 11 shows a format of a transmission slot. The transmission slotcomprises a pilot symbol portion (known sequence) and a data portion.FIG. 12 shows one example of impulse response of the transmission lineof frequency selective fading. In the mobile communication system, waves(multipath waves) having passed through a plurality of transmissionlines arrive due to reflection, diffraction, and scattering ofradio-waves resulting from the surrounding buildings and geographicalfeatures, and interfere with each other. Here is shown a case in which asignal that has become a multipath wave is input to a reception antenna.

The operation of the conventional receiver is explained next, withreference to FIG. 9 and FIG. 10. Signals from a mobile station receivedby N antennas 201-1 to 201-N are filtered by the BPFs 202-1 to 202-N,respectively, so that a desired band limitation is applied thereto. Thedespreading sections 203-1 to 203-N having received the band restrictedsignals perform despreading, using the same sequence as the spreadingcode sequence used on the transmission side.

The path detector 204 selects L paths from the despread signals affectedby the multipath waves, using one antenna output. Specifically, in thepath detector 204, at first, the transmission line estimating section300 uses a pilot symbol provided for each slot, to perform in-phaseaddition of all symbols in one slot to thereby obtain a momentaryestimate of the transmission line. The mean power value calculator 301performs power averaging processing over several slots, using thetransmission line estimate, to thereby calculate a mean power delayprofile. The threshold calculator 302 regards power in the path havingthe smallest power in the mean power delay profile as noise, anddesignates power larger by AdB than the power in the path having thesmallest power as a threshold for path selection. The judging section303 compares the mean power delay profile with the threshold, anddesignates the path having a mean power value larger than the thresholdas a multipath with respect to a desired signal, and outputs timewiseposition information and path power value of the path.

The respective beam forming sections generally perform signal processingwith respect to predetermined L paths, due to a limitation in hardwareor software. Therefore, in the path detector 204, at the end, the pathselecting section 304 selects L effective paths in decreasing order ofmean power value. The timewise position of the selected path is outputto the respective beam forming sections as the path positioninformation. The despread signals are separated for each path detectedby the path detector 204, and transmitted to the beam forming sections205-1 to 205-L.

The beam forming sections 205-1 to 205-L form beams for each detectedpath. Here, the beam forming section 205-1 performs the signalprocessing with respect to the first path, and the beam forming sections205-2 to 205-N sequentially perform the signal processing with respectto the second to the L-th path.

The operation of the respective beam forming sections is explained indetail below. The weight controller 223 calculates a weight based on theadaptive algorithm such as Least Mean Square (LMS), and the complexmultipliers 221-1 to 221-N multiply the signals received from therespective antennas by a complex weight for forming beams. The adder 224combines the signals output from the complex multipliers to generate asignal after the antenna combine, having directivity.

The transmission line estimating section 229 uses a pilot symbolprovided for each slot (see FIG. 11), to calculate a transmission lineestimate (complex value) for the first path. The complex conjugatecalculator 226 calculates a complex conjugate of the transmission lineestimate. The complex multiplier 225 multiplies the complex conjugate bythe combined signal output from the adder 224, and outputs a signalweighted in proportion to the signal amplitude, with phase fluctuationbeing removed.

The adder 206 having received signals from the first to the L-th pathsat the same time combines the phase-matched signals for each path.Lastly, the data judging section 207 performs hard judgment with respectto the output from the adder 206, and outputs the result as ademodulation result. Since the demodulation result is used as areference signal at the time of forming beams for each path, it isbranched and transmitted to the respective beam forming sections.

A method of determining a weight for each antenna by the adaptivealgorithm is explained below, using the beam forming section 205-1corresponding to the first path. At first, the complex multiplier 227performs complex multiplication of the output from the data judgingsection 207 and the output from the transmission line estimating section229, to generate the reference signal. The subtracter 228 performssubtraction processing of the output from the complex multiplier 227 andthe output from the adder 224, to generate an error signal e₁*(k) withrespect to the first path. Lastly, the weight controller 223 receivesthe error signal e₁*(k), and updates the weight as shown in thefollowing equation (1), based on the normalized LMS in the adaptivealgorithm: $\begin{matrix}{{W_{1}\left( {k + 1} \right)} = {{W_{1}(k)} + {\mu\frac{X_{1}\left( {k - \tau} \right)}{{{X_{1}\left( {k - \tau} \right)}}^{2}}{e_{1}^{*}(k)}}}} & (1)\end{matrix}$wherein ∥·∥ denotes a norm, k corresponds to the k-th sampling time(t=kT_(s): T_(s) denotes a sampling period), and * denotes a complexconjugate. X₁(k) is a vector expression of the first path of thedespread signals received by the respective antennas, and is such thatX₁(k)=[x₁(1, k), x₁(2, k), . . . , x₁(N, k)]^(T), W₁(k) is a vectorexpression of the weight for each antenna with respect to the firstpath, and is such that W₁(k)=[w₁(1, k), w₁(2, k), . . . , w₁(N, k)]^(T).The initial value of W₁(k) is W₁(0)=[1, 0, . . . , 0]^(T), μ denotes astep size, and τ denotes delay time necessary for a series of processinguntil the signal is input to the weight controller 223.

In the transmission line of frequency selective fading, the conventionalreceiver improves signal to interference ratio (SIR) relating to adesired signal, using a method in which the adaptive algorithm is usedwith respect to the path-detected L paths, to form beams separately, andweighting combine (RAKE combine) is performed corresponding to thetransmission line estimate, while directing null to the interferencesignal.

In the conventional receiver, however, since the incoming direction ofthe multipath from a mobile station to the base station cannot be known,in the initial state before forming the beams by the adaptive arrayantennas, beams having sharp directivity cannot be formed, and oneantenna having broad directivity is used. Therefore, when path detectionis performed by one antenna, and when the interference quantity islarge, there is a problem in that path detection cannot be performed athigh accuracy, corresponding to the signal quality in the path.

In the conventional receiver, from a reason similar to the above, aninitial value of the weight is set so as to use one antenna, in theinitial state when beams are formed by the adaptive array antennas. Inthis case, since much time is required for the processing of formingbeams based on the adaptive algorithm, on the transmission side of themobile station, much transmission signal power is required so that therequired quality can be satisfied on the reception side of the basestation, while signal processing until finishing beam formation isperformed on the base station side. Therefore, on the reception side ofthe base station, the interference power increases momentarily, therebymaking it difficult to obtain ideal channel capacity.

In the conventional receiver, it is necessary to prepare one adaptivealgorithm for each of the detected L paths, and hence there is a problemin that the hardware size increases.

In the conventional receiver, it is necessary to operate the adaptivealgorithm even for a path having a small reception power, if it is thedetected path. Therefore, the time required until the adaptive algorithmis settled increases, and hence there is a problem in that theinterference power cannot be sufficiently suppressed until thesettlement.

It is therefore an object of the present invention to provide anadaptive antenna receiver that can realize highly accurate pathdetection corresponding to the signal quality in the path and animprovement in reception quality, and can realize a reduction in thehardware and software size.

The adaptive antenna receiver according to one aspect of the presentinvention comprises a beam forming unit that uses a plurality ofantennas to forms beams having fixed directivity; a plurality ofdespreading units that separately despread a beam signal correspondingto the beams having fixed directivity; a path detecting unit thatdetects multipath waves on a transmission line based on the signalsobtained by despreding, and outputs path position information as adetection result; a transmission line estimating unit that estimates atransmission line for transmitting an adaptive beam combined signal foreach path, based on the path position information; a plurality ofcomplex multiplication units each of which separately complex multipliesthe despread signals by the transmission line estimation result for eachpath; an adaptive beam forming unit that generates a weight for eachpath by operating an adaptive algorithm for each path, using a pluralityof complex multiplication results and data judgment results in eachpath, and forms an adaptive beam combined signal for each path, usingthe weight and the despread signals; a phase matching unit that performsphase matching corresponding to the transmission line estimated by thetransmission line estimating unit, using the adaptive beam signal foreach path; a path combining unit that combines the adaptive beam signalsafter phase matching for all paths; and data judging unit that judgesthe data included in the adaptive beam signals combined.

The adaptive antenna receiver according to another aspect of the presentinvention comprises a beam forming unit that uses a plurality ofantennas to form beams having fixed directivity; a plurality ofdespreading units that separately despread a beam signal correspondingto the beams having fixed directivity; a path detecting unit thatdetects multipath waves on a transmission line based on the signalsobtained by despreding, and outputs path position information andpredetermined beam selection information necessary for operating theadaptive algorithm as a detection result; a transmission line estimatingunit that estimates the transmission line for transmitting an adaptivebeam combined signal for each path, based on the path positioninformation; a plurality of complex multiplication units each of whichseparately complex multiplies the despread signal by the transmissionline estimation result for each path; an adaptive beam forming unit thatgenerates a weight common to all paths by operating one adaptivealgorithm, using the complex multiplication results, data judgmentresults, and the beam selection information for all paths, and forms anadaptive beam combined signal for each path, using the weight common toall paths and the despread signals; a phase matching unit that performsphase matching corresponding to the transmission line estimated by thetransmission line estimating unit, using the adaptive beam signal foreach path; a path combining unit that combines the adaptive beam signalsafter phase matching for all paths; and a data judging unit that judgesthe data included in the adaptive beam signals combined.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 shows the configuration of a first embodiment of an adaptiveantenna receiver according to the present invention;

FIG. 2 shows the configuration of a path detector;

FIG. 3 shows patterns of H fixed beams generated by a beam formingsection;

FIG. 4 shows the configuration of a second embodiment of the adaptiveantenna receiver according to the present invention;

FIG. 5 shows the configuration of a third embodiment of the adaptiveantenna receiver according to the present invention;

FIG. 6 shows the configuration of a path detector;

FIG. 7 shows the configuration of a fourth embodiment of the adaptiveantenna receiver according to the present invention;

FIG. 8 shows the configuration of a fifth embodiment of the adaptiveantenna receiver according to the present invention;

FIG. 9 shows the configuration of a conventional receiver;

FIG. 10 shows the configuration of a conventional path detector;

FIG. 11 shows a format of a transmission slot; and

FIG. 12 shows one example of impulse response in a transmission line offrequency selective fading.

BEST MODE FOR CARRYING OUT THE INVENTION

Embodiments of the adaptive antenna receiver according to the presentinvention are explained in detail, with reference to the accompanyingdrawings. However, the present invention is not limited by thoseembodiments.

First Embodiment

FIG. 1 shows the configuration of the first embodiment of an adaptiveantenna receiver according to the present invention. This embodimentexplains an adaptive antenna receiver used in a mobile communicationsystem adopting a CDMA system. It is assumed that the format of thetransmission slot has the configuration shown in FIG. 11 describedearlier.

In FIG. 1, 101-1, 101-2, . . . , 101-N denote N antennas, 102-1, 102-2,. . . , 102-N denote N BPFs, 103 denotes a beam forming section thatforms a plurality of fixed directional beams, 104-1, 104-2, . . . ,104-H denote H despreading sections, 105 denotes a path detector, 106-1,106-2, . . . , 106-L denote L adaptive beam forming sections thatadaptively form beams using an adaptive algorithm for each detectedpath, 107 denotes an adder, and 108 denotes a data judging section.

In the respective adaptive beam forming section, 121-1, 121-2, . . . ,121-H, and 124-1, 124-2, . . . , 124-H denote complex multipliers, 125denotes an adder, 126 denotes a transmission line estimating sectionthat estimates a transmission line with respect to the individual path,127 denotes a complex conjugate calculator, 128 denotes a complexmultiplier, 122 denotes a delay device, and 123 denotes a weightcontroller.

FIG. 2 shows the configuration of the path detector 105. In the pathdetector 105, 401-1, 401-2, . . . , 401-H denote an beam path detectorsfor the first, the second, . . . , the H-th beams, 402 denotes a pathselecting section that selects a number of paths not exceeding L, fromthe output of the respective each beam path detectors. The path detector105 is for detecting a path from a despread signal for each of the firstto the H-th fixed beams. In the respective each beam path detector, 403denotes a transmission line estimating section, 404 denotes a mean powervalue calculator, 405 denotes a threshold calculator, and 406 denotes ajudging section. The configuration of all the beam path detectors issame, and hence the configuration of the each beam path detector 401-1is taken as an example for explanation.

The operation of the adaptive antenna receiver according to thisembodiment is explained in detail, with reference to the drawings. Atfirst, signals from a mobile station received by N antennas 101-1 to101-N are respectively filtered by the BPFs 102-1 to 102-N, so that adesired band limitation is applied thereto.

The beam forming section 103 receives the band-restricted signals, toform patterns of H fixed beams. FIG. 3 shows patterns of H fixed beamsgenerated by the beam forming section 103. The despreading sections104-1 to 104-N despread the signals received in H beams corresponding tothe arrival angle from the mobile station by using the same sequence asthe spreading code sequence (PN sequence) used on the transmission side.

The path detector 105 detects a path, using the despread signalsaffected by the multipath waves, and selects a number of paths notexceeding L, having a path position that differs timewise, in decreasingorder of path power. Specifically, in the each beam path detector 401-1,the transmission line estimating section 403 in-phase adds all symbolsin one slot, using a pilot symbol provided for each slot in the despreadsignal with respect to beam #1. By this averaging processing, atransmission line estimate in which the influence of noise is reducedcan be obtained. The mean power value calculator 404 performs poweraveraging processing over several slots, using the transmission lineestimate output from the transmission line estimating section 403, tocalculate a mean power delay profile in predetermined time. Thethreshold calculator 405 regards power in the path having the smallestpower in the mean power delay profile as noise and interference power,and sets power larger than the power in this path by optionallydetermined ΔdB as a threshold for the path selection. Lastly, thejudging section 406 compares the output from the mean power valuecalculator 404 with the output from the threshold calculator 405, andoutputs path position information representing a timewise position of apath exceeding the threshold and the mean power value of this path. Inthe second and the H-th each beam path detector, signal processingsimilar to that of the first each beam path detector 401-1 is carriedout.

The path selecting section 402 selects a number of paths not exceedingL, in decreasing order of path power, from the paths having differentpath positions detected by the first to the H-th beams. The pathselecting section 402 outputs the spatial and timewise path positions ofthe selected path to the adaptive beam forming section 106-1 to 106-L,as the path position information.

The operation of the respective adaptive beam forming sections isexplained below, taking the adaptive beam forming section 106-1corresponding to the first path as an example. Since the adaptive beamforming sections corresponding to the second to the L-th paths have thesame configuration as that of the adaptive beam forming section 106-1corresponding to the first path, the explanation thereof is omitted.

The adaptive beam forming section 106-1 receives despread signalsx_(i)(1, k), x_(i)(2, k), . . . , x_(i)(H, k) in the first path from thedespread signals of H beams, based on the first path positioninformation output from the path detector 105 (however, i means that itis the processing with respect to the i-th path, and i=1 herein).

The complex multipliers 124-1 to 124-H complex multiply weightsw_(i)*(1, k), w_(i)*(2, k), . . . , w_(i)*(H, k) of complex valuescalculated by the weight controller 123 by the despread signal in thefirst path (however, i means that it is the processing with respect toi-th path, and i=1 herein). The adder 125 adds the outputs from thecomplex multipliers 124-1 to 124-H, and the addition result becomes abeam signal (adaptive beam combined signal) having directivity.

The transmission line estimating section 126 calculates a transmissionline estimate (complex value) with respect to the first path, using thepilot symbol provided for each slot, shown in FIG. 11.

The complex conjugate calculator 127 calculates a complex conjugate ofthe transmission line estimate. The complex multiplier 128 multipliesthe output from the complex conjugate calculator 127 by the output fromthe adder 125, and outputs a signal weighted in proportion to the signalamplitude, with phase fluctuation being removed.

The adder 107 receives signal output corresponding to the first path andsignal outputs corresponding to the second to the L-th paths output bythe same processing, and combines an adaptive beam combined signal phasematched for each path. The data judging section 108 performs hardjudgment with respect to the output from the adder 107, and outputs theresult as a demodulation result. The demodulation result is branchedinto individual paths, and transmitted to the adaptive beam formingsections 106-1 to 106-L corresponding to the respective paths.

The output from the complex conjugate calculator 127 is transmitted tothe complex multipliers 121-1 to 121-H. The complex multipliers 121-1 to121-H perform complex multiplication of the despread signals of thefirst to the H-th beams and the output from the complex conjugatecalculator 127, to thereby calculate despread signals y_(i)(1, k),y_(i)(2, k), . . . , y_(i)(H, k) of the first to the H-th beams, inwhich a phase fluctuation component due to fading has been removed(however, i means that it is the processing with respect to the i-thpath, and i=1 herein). The delay device 122 delays the outputs of therespective complex multipliers 121-1 to 121-H by the processing delaytime τ (τ is a delay quantity for each discrete symbol) until thereference signal (that is, data judgment result) required for formingbeams is input to the weight controller 123.

The operation of the weight controller 123, that is, the weightdetermination method for each beam is explained below, taking an examplein which sample matrix inversion (hereinafter, “SMI”) is used as theadaptive algorithm for forming adaptive beams. The weight controller 123receives despread signals y_(i)(1, k−τ), y₁(2, k−τ), . . . , y₁(H, k−τ)in the first to the H-th beams corresponding to the first path, in whichthe delay quantity is adjusted, from the delay device 122 (however, kdenotes a number of a symbol representing discrete time, and τ denotes aprocessed delay quantity). Further, the weight controller 123 receives areference signal d(k−τ), being a demodulation result (it is a complexconjugate, k denotes a number of a symbol representing discrete time,and τ denotes a processed delay quantity), from the data judging section108.

If the output signal from the delay device 122 is expressed by a vector,the signal vector with respect to the first path becomes Y₁(k−τ)=[y₁(1,k−τ), y₁(2, k−τ), . . . , y₁(H, k−τ)]^(T), and the weight vector of theoutput from the weight controller 123 with respect to the first pathbecomes W₁(k)=[w₁(1, k), w₁(2, k), . . . , w₁(H, k)]^(T).

Therefore, the weight vector W₁(k) of the first path can be expressed bythe following equation (2):W ₁(k)=R _(Y1Y1)(k−τ)⁻¹ r _(Y1d)(k−τ)  (2)wherein R_(Y1Y1)(k) denotes a correlation matrix of the input vectorY₁(k), and r_(Y1d)(k) denotes a correlation vector.

When k−τ<1, or when the transmission frame is not continuouslytransmitted as at the time of packet transmission, beam forming isperformed by setting the weight to 1 with respect to the beam for whicha path has been detected, among the first to the H-th beams, and settingthe weight to 0 with respect to other beams, as the initial state of theweight vector W₁(k), based on the spatial position information (pathdetection information) of the path output from the path detector 105.For example, when position information indicating that the first path isdetected by the first beam is obtained, the adaptive beam formingsection 106-1 corresponding to the first path sets W₁(k)=[1, 0, . . . ,0]^(T), as the weight vector with respect to the first path.

The correlation matrix R_(Y1Y1)(k) can be expressed by the followingequation (3): $\begin{matrix}{{R_{Y\quad 1Y\quad 1}\left( {k - \tau} \right)} = {\frac{1}{m}{\sum\limits_{i = 1}^{m}{{Y_{1}\left( {k - \tau} \right)}{Y_{1}^{H}\left( {k - \tau - i} \right)}}}}} & (3)\end{matrix}$wherein ^(H) denotes a sign expressing complex conjugate transposition.

The correlation vector r_(Y1d)(k) with respect to the first path can beexpressed by the following equation (4): $\begin{matrix}{{r_{{Y1}\quad d}\left( {k - \tau} \right)} = {\frac{1}{m}{\sum\limits_{i = 1}^{m}{{Y_{1}\left( {k - \tau - i} \right)}{d^{*}\left( {k - \tau - i} \right)}}}}} & (4)\end{matrix}$wherein * denotes a complex conjugate.

Beams are then formed by the adaptive algorithm, using the weight vectorW₁(k) in the first path obtained by the equation (2). Here, calculationis performed recursively, according to the algorithm shown below,including the correlation vector r_(Y1d)(k), in order to simplify theinversion of the correlation matrix R_(Y1Y1)(k).

The correlation vector r_(Y1d)(k) can be calculated by the followingequation (5):r _(Y1d)(1)=Y ₁(1)d*(1)r _(Y1d)(k)=βr _(Y1d)(k−1)+(1−β)Y ₁(k)d*(k)k=2, 3,  (5)wherein β is a real number parameter satisfying 0<β<1, for controllingthe time constant for estimation.

The correlation matrix R_(Y1Y1)(k) can be calculated from the followingequation (6): $\begin{matrix}{{{R_{Y\quad 1Y\quad 1}^{- 1}(k)} = {{\frac{1}{\beta}{R_{Y\quad 1Y\quad 1}^{- 1}\left( {k - 1} \right)}} - \frac{\left( {1 - \beta} \right){R_{Y\quad 1Y\quad 1}^{- 1}\left( {k - 1} \right)}{Y_{1}(k)}{Y_{1}^{H}(k)}{R_{Y\quad 1Y\quad 1}^{- 1}\left( {k - 1} \right)}}{\beta^{2} + {{\beta\left( {1 - \beta} \right)}{Y_{1}^{H}(k)}{R_{Y\quad 1Y\quad 1}^{- 1}\left( {k - 1} \right)}{Y_{1}(k)}}}}}\quad{{k = 2},3,\quad\ldots}} & (6)\end{matrix}$

Therefore, based on the above equations (5) and (6), after phasematching R_(Y1Y1) ⁻¹(k−τ) and r_(Y1d)(k−τ) are calculated, thecalculation result is substituted in the equation (2), thereby theweight vector W₁(k) with respect to the first path can be calculated.

In this embodiment, an example in which the adaptive algorithm of SMI isused for determining the weight for forming the beams has beenexplained, but the adaptive algorithm is not limited to SMI, and forexample, a known adaptive algorithm such as RLS or LMS may be used.

In this embodiment, at the time of detecting the path, a plurality ofbeams having predetermined directivity is used to cover the serviceablearea, and path detection is carried out for each of the fixeddirectional beams. As a result, even when the interference quantity islarge in the area to be serviced, interference power for each of thefixed directional beams can be suppressed, and hence the path detectioncan be carried out accurately.

In this embodiment, further, the adaptive algorithm is operated by usingpredetermined fixed directional beams. As a result, the interferencequantity for each beam can be reduced, to increase the SIR. Therefore,the adaptive beams to be formed by the adaptive algorithm can be formedquickly.

In this embodiment, the adaptive beam combined signal phase matched foreach path is used, and the adaptive algorithm is utilized, to form theadaptive beams for each path. As a result, the communication quality canbe improved, while the fading fluctuation and the influence ofinterference received in the area to be serviced are reduced.

In this embodiment, when the weight is in the initial state, or whentransmission is not carried out continuously, as at the time of packettransmission, and when the adaptive algorithm of the adaptive antenna isin the initial state, the path detected for each of the fixeddirectional beams is weighted according to the signal level, and thencombined. As a result, the time required until the beam is formed, andthe adaptive algorithm is settled can be reduced, and the communicationquality can be improved, while the influence of interference received inthe area to be serviced is reduced.

Second Embodiment

In this embodiment, in addition to the configuration of the firstembodiment, an interference quantity estimating section, and anormalizing section that performs normalization, using the interferencequantity calculated by the interference quantity estimating section areprovided. The operation that is different from the first embodiment isonly explained here, for the brevity of explanation.

FIG. 4 shows the configuration of a second embodiment of the adaptiveantenna receiver according to the present invention. The operation ofthe interference quantity estimating section and the normalizing sectionis explained here. The format of the transmission slot is the same asthe one shown in FIG. 11. The components that are same as those in thefirst embodiment are denoted by the same reference sign, and theexplanation thereof is omitted.

In FIG. 4, 106 a-1, 106 a-2, . . . , 106 a-L denote L adaptive beamforming sections that adaptively form beams using the adaptivealgorithm, 129 denotes an interference quantity estimating section, and130 denotes a normalizing section.

Only the operation of the adaptive beam forming section 106 a-1corresponding to the first path is explained below, for the brevity ofexplanation. The interference quantity estimating section 129 in-phaseadds the pilot symbol P_(s)(k_(s), j) in the k_(s)-th slot for allsymbols, in order to calculate the interference quantity from the outputZ₁(k_(s), j) (k_(s) denotes a slot, and j denotes a j-th pilot symbol inthe k_(s)-th slot) of the adder 125, being the adaptive beam combinedsignal formed with respect to the first path (however, |P_(s)(k_(s),j)|=1), to calculate a transmission line estimate η₁(k_(s)) with respectto the k_(s)-th slot in the first path (however, η₁(k_(s)) is a complexnumber). In other words, the interference quantity estimating section129 calculates an interference quantity σ₁ ²(k_(s)) of the k_(s)-th slotwith respect to the adaptive beam combined signal in the first path, asshown in the following equation (7), using the transmission lineestimate η₁(k_(s)) and the adaptive beam combined signal Z₁(k_(s), j)with respect to the first path. $\begin{matrix}{{{\sigma_{1}^{2}\left( k_{s} \right)} = {\frac{1}{P}{\sum\limits_{j = 1}^{P}{{{{Z_{1}\left( {k_{s},j} \right)} \cdot {P_{s}^{*}\left( {k_{s},j} \right)}} - {\eta_{1}\left( k_{s} \right)}}}^{2}}}}\quad} & (7)\end{matrix}$wherein P_(s)*(k_(s), j) is a complex conjugate of P_(s)(k_(s), j), andP denotes the number of pilot symbols in one slot.

The interference quantity estimating section 129 averages the obtainedinterference quantity σ₁ ²(k_(s)) over a plurality of slots, accordingto the equation (8), to calculate an interference quantity estimateI₁(k) of the k_(s)-th slot in the adaptive beam combined signal in thefirst path. $\begin{matrix}{{l_{1}\left( k_{s} \right)} = {\frac{1}{S}{\sum\limits_{l = 0}^{S - 1}\quad{\sigma_{1}^{2}\left( {k_{s} - S} \right)}}}} & (8)\end{matrix}$wherein S denotes the number of slots used for averaging.

After phase matching, the normalizing section 130 having received theoutput of the interference quantity estimating section 129 and theoutput of the complex multiplier 128 generates the adaptive beamcombined signal in the first path normalized by the interferencequantity, by dividing the output of the complex multiplier 128 by theoutput of the interference quantity estimating section 129.

In this embodiment, when a mobile station having a differenttransmission signal power exists, because the position of the mobilestation is unevenly distributed momentarily, or the transmission rate isdifferent, and hence the interference power for each beam formed by theadaptive array antennas cannot be regarded as the same, weighting isperformed corresponding to the interference quantity, and then theadaptive beam combined signals for each path are combined. As a result,the same effect as that of the first embodiment can be obtained, and thereception SIR can be maximized, and hence ideal channel capacity can beobtained.

Third Embodiment

In this embodiment, the input signal to the weight controller is for thenumber of fixed directional beams, and the weight generated by theweight controller is applied to all paths. In other words, there is oneweight controller on the receiver side in the base station with respectto each mobile station. Here, only the operation different from that ofthe first embodiment is explained.

FIG. 5 shows the configuration of the third embodiment of the adaptiveantenna receiver according to the present invention. The construction inFIG. 11 is used for the format of the transmission slot, as in the firstembodiment. The component same as that in the first embodiment isdenoted by the same reference sign, and the explanation thereof isomitted.

In FIG. 5, 105 b denotes a path detector, and 106 b-1, 106 b-2, . . . ,106 b-L denote adaptive beam forming sections that adaptively formsbeams, using the adaptive algorithm, for each of the detected paths, and123 b denotes a weight controller.

FIG. 6 shows the configuration of the path detector 105 b. In FIG. 6,401 b-1, 401 b-2, . . . , 401 b-H respectively denote an each beam pathdetector in the first, the second, . . . , and the H-th beams, 402denotes a path selecting section, and 407 denotes a beam selectingsection that selects a beam having the best reception condition from aplurality of fixed beams. The path detector 105 b detects a path fromthe despread signals for each of the first to the H-th fixed beams, andselects a beam having the best reception condition.

The operation of the adaptive antenna receiver in this embodiment isexplained in detail, with reference to the drawings. Only the operationsthat are different from those of the first embodiment are explainedhere. In the path detector 105 b, the beam selecting section 407calculates the sum total of path power for each beam, by using theinformation relating to the path position (timewise), the path position(spatial), and the path power value, in addition to the operation in thefirst embodiment, and selects a beam having the largest sum total of thepath power, and then outputs the beam selection result to the weightcontroller 123 b.

The operation of the adaptive beam forming section 106 b-1 correspondingto the first path and the weight controller 123 b is explained below.The adaptive beam forming sections corresponding to the second to theL-th paths have the same configuration as that of the adaptive beamforming section 106 b-1, and hence the explanation thereof is omitted.Further, only the operation different from that of the first embodimentis explained here.

The adaptive beam forming section 106 b-1 receives despread signalsx_(i)(1, k), x_(i)(2, k), . . . , x_(i)(H, k) in the first path from thedespread signals of H beams, based on the first path positioninformation output from the path detector 105 b.

The complex multipliers 124-1 to 124-H complex multiply weights w(1, k),w(2, k), . . . , w(H, k) of complex values common to all pathscalculated by the weight controller 123 b by the despread signal in thefirst path. The adder 125 adds the outputs from the complex multipliers124-1 to 124-H, and the addition result becomes a beam signal (adaptivebeam combined signal) having directivity.

The transmission line estimating section 126 calculates a transmissionline estimate (complex value) with respect to the first path, using thepilot symbol provided for each slot, shown in FIG. 11. The complexconjugate calculator 127 calculates a complex conjugate of thetransmission line estimate. The complex multiplier 128 multiplies theoutput from the complex conjugate calculator 127 by the output from theadder 125, and outputs a signal weighted in proportion to the signalamplitude, with phase fluctuation being removed.

The adder 107 receives signal output corresponding to the first path andsignal outputs corresponding to the second to the L-th paths output bythe same processing, and combines an adaptive beam combined signal phasematched for each path. The data judging section 108 performs hardjudgment with respect to the output from the adder 107, and outputs theresult as a demodulation result. The demodulation result is transmittedto the weight controller 123 b as a reference signal.

The output from the complex conjugate calculator 127 is transmitted tothe complex multipliers 121-1 to 121-H. The complex multipliers 121-1 to121-H perform complex multiplication of the despread signals of thefirst to the H-th beams and the output from the complex conjugatecalculator 127, to thereby calculate despread signals y_(i)(1, k),y_(i)(2, k), . . . , y_(i)(H, k) of the first to the H-th beams, inwhich a phase fluctuation component due to fading has been removed(however, i means that it is the processing with respect to the i-thpath, and i=1 herein). The delay device 122 delays the outputs of therespective complex multipliers 121-1 to 121-H by the processing delaytime τ (τ is a delay quantity for each discrete symbol) until thereference signal (that is, data judgment result) required for formingbeams is input to the weight controller 123 b. The delay time of thefirst to the H-th beam signals after phase matching the complexmultiplication, which has been delayed for each path, received by theweight controller 123 b is matched, so as to be input at an accuracy ofsymbol timing.

The operation of the weight controller 123 b, that is, the weightdetermination method for each beam is explained below, taking an examplein which SMI is used as the adaptive algorithm for forming adaptivebeams. The weight controller 123 b receives despread signals y_(i)(1,k−τ), y₁(2, k−τ), . . . , y_(i)(H, k−τ) in the first to the H-th beamscorresponding to the first path, in which the delay quantity isadjusted, from the delay device 122 (however, k denotes a number of asymbol representing discrete time, and τ denotes a processed delayquantity). Further, the weight controller 123 b receives a referencesignal d(k−τ), being a demodulation result (it is a complex conjugate),from the data judging section 108.

The signal vector with respect to the first path becomesY_(i)(k−τ)=[y_(i)(1, k−τ), y_(i)(2, k−τ), . . . , y_(i)(H, k−τ)]^(T),and the weight vector of the output from the weight controller 123 bwith respect to all paths becomes W(k)=[w(1, k), w(2, k), . . . , w(H,k)]^(T).

Therefore, the weight vector W₁(k) of the first path can be expressed bythe following equation (9):W(k)=R _(YY)(k−τ)⁻¹ r _(Yd)(k−τ)  (9)wherein R_(YY)(k) denotes a correlation matrix of a signal obtained bycombining the signal vector Y_(i)(k) in each path, as shown in thefollowing equation (10): $\begin{matrix}{{R_{YY}\left( {k - \tau} \right)} = {\frac{1}{m\quad L}{\sum\limits_{j = 1}^{L}\quad{\sum\limits_{i = 1}^{m}\quad{{Y_{j}\left( {k - \tau} \right)}{Y_{j}^{H}\left( {k - \tau - i} \right)}}}}}} & (10)\end{matrix}$wherein L denotes the number of paths r_(Yd)(k) denotes a correlationvector of a signal obtained by combining the signal vector Y_(i)(k) ineach path, as shown in the following equation (11): $\begin{matrix}{{R_{YY}\left( {k - \tau} \right)} = {\frac{1}{m\quad L}{\sum\limits_{j = 1}^{L}\quad{\sum\limits_{i = 1}^{m}\quad{{Y_{j}\left( {k - \tau} \right)}{Y_{j}^{H}\left( {k - \tau - i} \right)}}}}}} & (11)\end{matrix}$

When k−τ<1, or when the transmission frame is not continuouslytransmitted as at the time of packet transmission, beam forming isperformed by setting the weight to 1 with respect to the beam having thelargest sum total of the path power, among the first to the H-th beams,and setting the weight to 0 with respect to other beams, as the initialstate of the weight vector W(k), based on the beam selection signaloutput by the path detector 105 b. For example, when the beam selectionsignal indicating that the sum total of the path power of the first beamis the largest is obtained, the weight controller 123 b sets W(k)=[1, 0,. . . , 0]^(T), as the weight vector.

Further, beam formation by the adaptive algorithm is carried out, usingthe weight vector W(k) obtained by the equation (9). Here, calculationprocessing is performed recursively, according to the algorithm shownbelow, including the correlation vector r_(Yd)(k), in order to simplifythe inversion of the correlation matrix R_(YY)(k). The correlationvector r_(Yd)(k) can be calculated by the following equation (12):$\begin{matrix}\begin{matrix}{{r_{Y\quad d}(1)} = {\sum\limits_{j = 1}^{L}{{Y_{j}(1)}{d^{*}(1)}}}} \\{{r_{Yd}(k)} = {{\beta\quad{r_{Y\quad d}\left( {k - 1} \right)}} + {\left( {1 - \beta} \right){\sum\limits_{j = 1}^{L}{{Y_{j}(k)}{d^{*}(k)}}}}}}\end{matrix} & (12)\end{matrix}$wherein β is a real number parameter satisfying 0<β<1, for controllingthe time constant for estimation.

The correlation matrix R_(YY)(k) can be calculated from the followingequation (13): $\begin{matrix}{{{R_{{Y\quad Y}\quad}^{- 1}(k)} = {{\frac{1}{\beta}{R_{YY}^{- 1}\left( {k - 1} \right)}} - \frac{\left( {1 - \beta} \right){R_{YY}^{- 1}\left( {k - 1} \right)}{\sum\limits_{j = 1}^{L}{{Y_{j}(k)} \cdot {\sum\limits_{j = 1}^{L}{{Y_{j}^{H}(k)} \cdot {R_{YY}^{- 1}\left( {k - 1} \right)}}}}}}{\beta^{2} + {{\beta\left( {1 - \beta} \right)}{\sum\limits_{j = 1}^{L}{{{Y_{j}^{H}(k)} \cdot {R_{YY}^{- 1}\left( {k - 1} \right)}}{\sum\limits_{j = 1}^{L}{Y_{j}(k)}}}}}}}}\quad{{k = 2},3,\quad\ldots}} & (13)\end{matrix}$

Therefore, based on the above equations (12) and (13), after phasematching R_(YY) ⁻¹(k−τ) and r_(Y1d)(k−τ) are calculated, the calculationresult is substituted in the equation (9), thereby the weight vectorW(k) can be calculated.

In this embodiment, an example in which the adaptive algorithm of SMI isused for determining the weight for forming the beams has beenexplained, but the adaptive algorithm is not limited to SMI, and forexample, a known adaptive algorithm such as RLS or LMS may be used.

In this embodiment, a signal obtained by combining the adaptive beamcombined signals phase matched for each path over all paths is used, togenerate a weight common to all paths by using the adaptive algorithm.Thereby, on the reception side of the base station, one adaptivealgorithm corresponding to the number of fixed directional beams needsonly to be prepared. As a result, the size of hardware and software canbe considerably reduced.

In this embodiment, when the weight is in the initial state, or whentransmission is not carried out continuously, as at the time of packettransmission, and when the adaptive algorithm of the adaptive antenna isin the initial state, the adaptive algorithm is operated by selecting abeam having the largest sum total of path power from the fixeddirectional beams. As a result, the time until the adaptive algorithm issettled can be reduced, and the communication quality can beconsiderably improved, while the interference quantity in the area to beserviced is reduced.

Fourth Embodiment

In addition to the third embodiment, this embodiment corresponds to acase in which there exists a path whose incoming direction is largelydifferent spatially. Specifically, a combination of the adaptive beamforming sections 106 b-1 to 106 b-L, the weight controller 123 b, andthe adder 107 is provided for a plurality of groups. Here, only theoperation different from that of the third embodiment is explained.

FIG. 7 shows the configuration of the fourth embodiment of the adaptiveantenna receiver according to the present invention. The construction inFIG. 11 is used for the format of the transmission slot, as in the firstto the third embodiments. The component same as that in the thirdembodiment is denoted by the same reference sign, and the explanationthereof is omitted.

In FIG. 7, 105 c denotes a path detector having the same function as thepath detector 105 described above, 141 denotes an adder, and 151-1 to151-M denote an adaptive beam forming group formed of a combination ofthe adaptive beam forming sections 106 b-1 to 106 b-L, the weightcontroller 123 b, and the adder 107.

The operation of the adaptive antenna receiver in this embodiment isdescribed below in detail, with reference to the drawings. Here, onlythe operation different from that of the third embodiment is explained.For example, a path is detected in two or more fixed beams by the pathselecting section 402 shown in FIG. 6, and a plurality of adaptive beamforming groups are provided so as to correspond to an individual path,with respect to paths different spatially such that the path positionexceeds the adjacent fixed directional beams, to thereby form beamsadaptively.

The outputs of the adaptive beam forming groups are added in the adder141, and the addition result is output to the data judging section 108.

As described above, in this embodiment, when the path detection positionis largely different spatially, an adequate adaptive beam is formed foreach group of paths detected at close positions spatially. As a result,the similar effect to that of the third embodiment can be obtained, andadaptive beams can be formed without increasing the number of weightcontrollers that execute the adaptive algorithm.

Fifth Embodiment

This embodiment corresponds to a case in which there exists a path whoseincoming direction is largely different spatially, with processingdifferent from the third embodiment. Specifically, a combination of theadaptive beam forming sections 106 d-1 to 106 d-L (application exampleof the second embodiment), the weight controller 123 b, and the adder107 is provided for a plurality of groups. Here, only the operationdifferent from that of the fourth embodiment is explained.

FIG. 8 shows the configuration of the fifth embodiment of the adaptiveantenna receiver according to the present invention. The construction inFIG. 11 is used for the format of the transmission slot, as in the firstto the fourth embodiments. The component same as that in the first tofourth embodiments is denoted by the same reference sign, and theexplanation thereof is omitted.

In FIG. 8, 106 d-1, 106 d-2, . . . , 106 d-L denote an adaptive beamforming section that adaptively forms beams, using the adaptivealgorithm for each of the detected paths, and 151 d-1 to 151 d-M denotean adaptive beam forming group formed of a combination of the adaptivebeam forming sections 106 d-1 to 106 d-L, the weight controller 123 b,and the adder 107. The interference quantity estimating section 129 andthe normalizing section 130 in the adaptive beam forming sections 106d-1 to 106 d-L operate in the same manner as in the second embodiment,to estimate the interference quantity, using the pilot symbol in theslot.

As described above, in this embodiment, an effect similar to that of thefourth embodiment can be obtained, and further, since the constructionis such that normalization is performed for each path according to theinterference quantity, for example, even when the interference quantityis different for each of the formed adaptive beams, the reception SIRcan be increased.

As explained above, according to the present invention, the adaptivealgorithm is operated, by using predetermined fixed directional beams.Thereby, the interference quantity for each beam is reduced, to increasethe SIR. As a result, there is the effect that the adaptive beams formedby the adaptive algorithm can be formed quickly. Further, the adaptivebeam combined signal phase matched for each path is used, to form theadaptive beams for each path, by using the adaptive algorithm. As aresult, the communication quality can be increased, while reducing theinfluences of fading fluctuation and interference received in the areato be serviced.

According to the next invention, when a mobile station having adifferent transmission signal power exists, because the position of themobile station is unevenly distributed momentarily, or the transmissionrate is different, and hence the interference power for each beam formedby the adaptive array antennas cannot be regarded as the same, weightingis performed corresponding to the interference quantity, and then theadaptive beam combined signals for each path are combined. As a result,the reception SIR can be maximized, and hence ideal channel capacity canbe obtained.

According to the next invention, at the time of path detection, aplurality of beams having predetermined directivity is used to cover theserviceable area, and path detection is performed for each of the fixeddirectional beams. As a result, even when the interference quantity islarge in the area to be serviced, the interference power is suppressedfor each of the fixed directional beams, and hence path detection can beaccurately performed.

According to the next invention, a signal obtained by combining theadaptive beam combined signals phase matched for each path over allpaths is used, to generate a weight common to all paths by using theadaptive algorithm. Thereby, on the reception side of the base station,one adaptive algorithm corresponding to the number of fixed directionalbeams needs only to be prepared. As a result, the size of hardware andsoftware can be considerably reduced.

According to the next invention, when the path detection position islargely different spatially, an adequate adaptive beam is formed foreach group of paths detected at close positions spatially. As a result,adaptive beams can be formed without increasing the number of theadaptive algorithm.

According to the next invention, since the construction is such thatnormalization is performed for each path, for example, even when theinterference quantity is different for each of the formed adaptivebeams, the reception SIR can be increased.

According to the next invention, at the time of path detection, aplurality of beams having predetermined directivity is used to cover theserviceable area, and path detection is performed for each of the fixeddirectional beams. As a result, even when the interference quantity islarge in the area to be serviced, the interference power is suppressedfor each of the fixed directional beams, and hence path detection can beaccurately performed.

According to the next invention, when the weight is in the initialstate, and when the adaptive algorithm of the adaptive antenna is in theinitial state, the path detected for each of the fixed directional beamsis weighted corresponding to the signal level, and combined. As aresult, the time required until the beams are formed and the adaptivealgorithm is settled can be reduced.

INDUSTRIAL APPLICABILITY

As described above, the adaptive antenna receiver according to thepresent invention is suitable for a mobile communication system adoptingthe CDMA system using the spread spectrum modulation system, and isuseful for a transmission line of frequency selective fading, in whichmultipath waves interfere with each other due to reflection,diffraction, and scattering of radio waves resulting from thesurrounding buildings and geographical features.

1. An adaptive antenna receiver comprising: a beam forming unit thatuses a plurality of antennas to forms beams having fixed directivity; aplurality of despreading units that separately despread a beam signalcorresponding to the beams having fixed directivity; a path detectingunit that detects multipath waves on a transmission line based on thesignals obtained by despreding, and outputs path position information asa detection result; a transmission line estimating unit that estimates atransmission line for transmitting an adaptive beam combined signal foreach path, based on the path position information; a plurality ofcomplex multiplication units each of which separately complex multipliesthe despread signals by the transmission line estimation result for eachpath; an adaptive beam forming unit that generates a weight for eachpath by operating an adaptive algorithm for each path, using a pluralityof complex multiplication results and data judgment results in eachpath, and forms an adaptive beam combined signal for each path, usingthe weight and the despread signals; a phase matching unit that performsphase matching corresponding to the transmission line estimated by thetransmission line estimating unit, using the adaptive beam signal foreach path; a path combining unit that combines the adaptive beam signalsafter phase matching for all paths; and a data judging unit that judgesthe data included in the adaptive beam signals combined.
 2. The adaptiveantenna receiver according to claim 1, further comprising: aninterference quantity estimating unit that estimates an interferencequantity from the adaptive beam combined signal for each path, based ona known sequence added to a transmission slot; and a normalizing unitthat normalizes the adaptive beam signal after phase matching, based onthe estimated interference quantity for each path, wherein the pathcombining unit combines the adaptive beam signals after phase matchingnormalization for all paths.
 3. The adaptive antenna receiver accordingto claim 1, wherein the path detecting unit includes a plurality of eachbeam path detecting units each of which uses the signal afterdespreading for each beam to obtain a path position and a path powervalue separately; and a path selecting section that selects apredetermined number of paths in decreasing order of path power value,from paths having different path positions, and outputs path positioninformation as a selection result, and each of the each beam pathdetecting units includes an in-phase addition unit that in-phase addsall symbols in one slot, by using a known sequence provided for eachslot of the despread signal for each beam; a mean power delay profileunit that performs averaging processing of power over several slots byusing the in-phase addition result, to generate a mean power delayprofile; a threshold generating unit that generates a threshold forselecting a path, based on the mean power delay profile; and acomparison unit that compares the mean power delay profile with thethreshold, and outputs a path position of a path exceeding the thresholdand the path power value.
 4. The adaptive antenna receiver according toclaim 1, wherein when the adaptive algorithm is in an initial state, theadaptive beam forming unit sets the weight to 1 with respect to the beamfor which a path has been detected, and sets the weight to 0 withrespect to other beams.
 5. An adaptive antenna receiver comprising: abeam forming unit that uses a plurality of antennas to form beams havingfixed directivity; a plurality of despreading units that separatelydespread a beam signal corresponding to the beams having fixeddirectivity; a path detecting unit that detects multipath waves on atransmission line based on the signals obtained by despreding, andoutputs path position information and predetermined beam selectioninformation necessary for operating an adaptive algorithm as a detectionresult; a transmission line estimating unit that estimates thetransmission line for transmitting an adaptive beam combined signal foreach path, based on the path position information; a plurality ofcomplex multiplication units each of which separately complex multipliesthe despread signal by the transmission line estimation result for eachpath; an adaptive beam forming unit that generates a weight common toall paths by operating one adaptive algorithm, using the complexmultiplication results, data judgment results, and the beam selectioninformation for all paths, and forms an adaptive beam combined signalfor each path, using the weight common to all paths and the despreadsignals; a phase matching unit that performs phase matchingcorresponding to the transmission line estimated by the transmissionline estimating unit, using the adaptive beam signal for each path; apath combining unit that combines the adaptive beam signals after phasematching for all paths; and a data judging unit that judges the dataincluded in the adaptive beam signals combined.
 6. The adaptive antennareceiver according to claim 5, further comprising: a plurality ofadaptive beam forming groups formed of a combination of the transmissionline estimating unit, the complex multiplication unit, the adaptive beamforming unit, the phase matching unit, and the path combining unit; anda group combining unit that combines outputs from the adaptive beamforming groups, wherein the data judging unit judges the data includedin the signal output from the group combining unit.
 7. The adaptiveantenna receiver according to claim 5, further comprising: a pluralityof adaptive beam forming groups formed of a combination of thetransmission line estimating unit, the complex multiplication unit, theadaptive beam forming unit, the phase matching unit, an interferencequantity estimating unit that estimates the interference quantity fromthe adaptive beam combined signal for each path based on a knownsequence added to the transmission slot, a normalizing unit thatnormalizes the adaptive beam signal after phase matching, based on theinterference quantity estimated for each path, and a path combining unitthat further combines the outputs from the adaptive beam forming groups,wherein the data judging unit judges the data included in the signaloutput from the group combining unit.
 8. The adaptive antenna receiveraccording to claim 5, wherein the path detecting unit includes aplurality of each beam path detecting units each of which uses thedespread signal for each beam to obtain a path position and a path powervalue separately; and a path selecting section that selects apredetermined number of paths in decreasing order of path power value,from paths having different path positions, and outputs path positioninformation as a selection result, and each of the each beam pathdetecting units includes an in-phase addition unit that in-phase addsall symbols in one slot, by using a known sequence provided for eachslot of the despread signal for each beam; a mean power delay profileunit that performs averaging processing of power over several slots byusing the in-phase addition result, to generate a mean power delayprofile; a threshold generating unit that generates a threshold forselecting a path, based on the mean power delay profile; a comparisonunit that compares the mean power delay profile with the threshold, andoutputs a path position of a path exceeding the threshold and the pathpower value; and a beam selection information generating unit thatcalculates the sum total of the path power for each beam based on thepath position and the path power value, and selects a beam having thelargest sum total, to generate beam selection information as a selectionresult.
 9. The adaptive antenna receiver according to claim 5, whereinwhen the adaptive algorithm is in an initial state, the adaptive beamforming unit sets the weight to 1 with respect to the beam for which apath has been detected, and sets the weight to 0 with respect to otherbeams.